AC-DC Switch Mode Power Supply Design Guide
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AC/DC Switch Mode Power Supply Design Guide
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AC/DC Switch Mode Power Supply Design Guide
Table Of Contents
Product Information Total Solutions.........................................................................................................................................3 Fairchild Power Switch (FPS™) ...............................................................................................................4-5 Pulse Width Modulator (PWM) Controllers .................................................................................................6 Power Factor Correction (PFC) Controllers..................................................................................................7 Optocoupler Solutions .............................................................................................................................8 Voltage References and Shunt Regulators ...................................................................................................9 High Voltage Switching Technologies.......................................................................................................10 Switch Mode Power Supply IGBTs...........................................................................................................10 High-Voltage MOSFETs ..........................................................................................................................11 Additional Discrete Components .............................................................................................................12 Design Examples Examples of Typical Application Circuits .............................................................................................13-22 1W Power Supply with less than 100mW Standby Power using FSD210 ..........................................13 Dual Negative Output Non-Isolated Flyback using FSD200...............................................................14 10W Single Output Isolated Flyback using FSDM0265RN and Zener Diode .....................................15 10W Multiple Output Isolated Flyback using FSD210 with Primary Side Regulation ...........................16 2.5W Single Output Isolated Flyback using FSD200 with KA431 Reference......................................17 180W-200W Quasi-Resonant Flyback with Input Power Factor Correction using KA5Q1265RF, FAN7527B, and FQP13N50C ....................................................................................................18-19 16W Multiple Output Isolated Flyback Converter using FSDM0265RN .............................................20 40W Isolated Flyback Power Supply using FSDM07652R ................................................................21 24W Flyback Converter using 1500V IGBT and FAN7554 ..............................................................22 Design Ideas 250W to 450W Desktop PC Forward Switch Mode Power Supply.......................................................23 500W Telecom/Server Double Switch Forward Switch Mode Power Supply..........................................24 500W Telecom/Server ZVS Phase-Shift Full Bridge Switch Mode Power Supply .....................................25 Application Note Highlights Design Guidelines for Off-Line Flyback Converters using Fairchild Power Switch (FPS) – AN-4137 ............26-27 Power Factor Correction (PFC) Basics – AN-42047...................................................................................28 Choosing Power Switching Devices for SMPS Designs – AN-7010........................................................29-30 Global Power Resources™ Design Support .....................................................................................................................................31
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2
AC/DC Switch Mode Power Supply Design Guide
Total Solutions Fairchild is the only semiconductor supplier that provides a complete portfolio for AC/DC switch mode power supplies. Whether your design is 1W or 1200W, Fairchild's solutions help achieve increased efficiency, reduce stand-by power, and support the industry's 1W initiatives. These solutions include: SuperFET™ technology that achieves world-class RDS(ON) and provides higher power density, reducing heat sink size, Green Fairchild Power Switch (FPS) that offers state-of-the-art stand-by power supporting the industry's initiatives targeting less than 1W, and Power Factor Correction ICs that decrease cost and increase system efficiency.
SMPS IGBTs
High Voltage MOSFETs
• Increase output power • Reduce system cost • Stealth™ Diode Co-Pack enhances recovery time
• • • •
25% lower A * RDS(ON) minimizes system size 100% Avalanche tested Voltage ranges from 60V to 1000V SuperFET offers best in class FOM
Power Factor Correction (PFC) Controllers
Additional Discrete Components
Voltage References/Shunt Regulators
• Increase efficiency • Increase usable PFC bandwidth and simplifiy compensation • Reduce ripple voltage and output capacitor size • Reduce EMI and system noise
• Low-Voltage MOSFETs • MOSFET and Schottky Combos • Diodes and Rectifiers • Bipolar Transistors and JFETs
• • • •
PFC Controller or PFC/PWM Controller
AC Input
Input Filter
MOSFET/ IGBT Switch
MOSFET Switch
Bridge Rectifier
PWM Controller
Transformer
Fairchild Power Switch
Output Rectifier or MOSFET
Optocoupler
Programmable output voltages Temperature compensated Low output noise Fast turn-on time
Output Filter
Load
Voltage Reference
Optically Isolated Error Amplifier
PWM Controller • Gr een c u r r en t m o d e r ed u c es p o w er c o n s u m p t i o n w i t h b u r s t m o d e o p er at i o n • In t er n al s t ar t -u p s w i t c h • Pr o g r am m ab l e s o f t s t ar t • Ov er Vo l t ag e Pr o t ec t i o n (OVP)
Optically Isolated Error Amplifier
Fairchild Power Switch (FPS) • Green FPS reduces power consumption with burst mode operation • Avalanche rated SenseFET™ • Frequency modulation reduces EMI • Built in soft start
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• Single component solution vs. 2 components • High isolation, 5,000V RMS • Low tolerance results in easier design, fewer components • Save board space
Optocoupler • MICROCOUPLER™ offers stable CTR up to 125°C • Narrow Current Transfer Ratio (CTR) • Multiple package types for ease of use
AC/DC Switch Mode Power Supply Design Guide
Fairchild Power Switch (FPS) Fairchild's FPS products are highly integrated off-line power switches with a fully avalanche rated SenseFET and a current mode PWM IC (see Burst Mode Operation figure below). The Green FPS products help reduce the system's stand-by power to below 1Watt with the burst mode operation. • Advanced burst mode operation supports 1W standby power regulations • Integrated frequency modulation reduces EMI emissions
FPS Parallel Dice Solution (Side-by-Side) Ipk
FB
Vcc
GND
FPS Single Die Solution (BCDMOS) VFB
GND
GND
GND
Drain
Vstr
• Various protection and control functions reduce Bill-of-Material costs PWM IC
SenseFET
Burst Mode Operation Reduces Stand-By Power to Less than 1W Vstr
Drain
Drain
Drain
Vcc
Burst Operation
Feedback Waveform
Normal Operation
VBURSTH
VBURSTL Current Waveform Not Switching
Not Switching
Frequency Modulation Reduces Overall Electromagnetic Interference (EMI)
Peak Level Limit Peak Level Limit
Peak Waveform
Quasi Peak Waveform
100kHz 100kHz Fixed FixedFrequency Frequency FSDH0165 FSDH0165
134kHz Modulation 134kHzwith withFrequency Frequency Modulation FSD210 FSD210
EMI reduction can be accomplished by modulating the switching frequency of a SMPS. Frequency modulation can reduce EMI by spreading the energy over a wider frequency range.
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AC/DC Switch Mode Power Supply Design Guide
Fairchild Power Switch (FPS) Green FPS Part Number
Application
PO(max) (W) 85-265VAC
PO(max) (W) 230VAC ±15%
Peak Current HV-FET Rating Limit (A) (V)
RDS(ON) max (Ω)
Switching Frequency (V)
Frequency Mod. (kHz)
Package TO220-5L
FSCM0565RC
STB, LCD Monitor
70
85
2.5
650
2.2
66
Yes
FSCM0565RD
STB, LCD Monitor
50
65
2.5
650
2.2
66
Yes
D2PAK-5L
FSCM0765RC
STB, LCD Monitor
85
95
3
650
1.6
66
Yes
TO220-5L
FSCM0765RD
STB, LCD Monitor
60
70
3
650
1.6
66
Yes
D2PAK-5L
FSCQ0765RT
CTV, DVD, Audio Electronics
85
100
5
650
1.6
QRC
No
TO220F-5L
FSCQ1265RT
CTV, DVD, Audio Electronics
140
170
7
650
0.9
QRC
No
TO220F-5L
FSCQ1565RP
CTV, DVD, Audio Electronics
210
250
11.5
650
0.65
QRC
No
TO3PF-7L
FSCQ1565RT
CTV, DVD, Audio Electronics
170
210
8
650
0.65
QRC
No
TO220F-5L
FSD1000
PC Main + Aux , LCD
12
13.6
Adjustable
700
9
70
No
DIPH-12
FSD200B
Charger, Aux Power
5
7
0.3
700
32
134
Yes
LSOP-7
FSD200BM
Charger, Aux Power
5
7
0.3
700
32
134
Yes
DIP-7
FSD210B
Charger, Aux Power
5
7
0.3
700
32
134
Yes
DIP-7
FSD210BM
Charger, Aux Power
5
7
0.3
700
32
134
Yes
LSOP-7
FSDH0265RL
DVDP, STB, Fax, Printer, Scanner, Adapters
20
27
1.5
650
6
100
Yes
LSOP-8
FSDH0265RN
DVDP, STB, Fax, Printer, Scanner, Adapters
20
27
1.5
650
6
100
Yes
DIP-8
PC Aux, STB, DVD,
12
17
0.7
650
19
100
Yes
DIP-8
PC Aux, STB, DVD, Adapters
12
17
0.7
650
19
100
Yes
LSOP-8
FSDL0165RL
DVDP, STB, Printer, Fax, Scanner, Adapters
12
23
1.2
650
10
50
Yes
LSOP-8
FSDL0165RN
DVDP, STB, Printer, Fax, Scanner, Adapters
12
23
1.2
650
10
50
Yes
DIP-8
FSDL0365RL
DVDP, STB, Printer, Fax,
24
30
2.15
650
4.5
50
Yes
LSOP-8
24
30
2.15
650
4.5
50
Yes
DIP-8
12
17
0.7
650
19
50
Yes
DIP-8
12
17
0.7
650
19
50
Yes
LSOP-8
FSDM0265RNB DVDP, STB, Fax, Printer, Scanner, Adapters
20
27
1.5
650
6
67
Yes
DIP-8
FSDM0365RL
DVDP, STB, Fax, Printer, Scanner, Adapters
24
30
2.15
650
4.5
67
Yes
LSOP-8
FSDM0365RNB DVDP, STB, Fax, Printer, Scanner, Adapters
24
30
2.15
650
4.5
67
Yes
DIP-8
FSDH321
Adapters FSDH321L
Scanner, Adapters FSDL0365RNB
DVDP, STB, Printer, Fax, Scanner, Adapters
FSDL321
PC Aux, STB, DVD, Adapters
FSDL321L
PC Aux, STB, DVD, Adapters
FSDM0565RB
LCD ,STB, Adapters
48
56
2.3
650
2.2
66
No
TO220F-6L
FSDM07652RB
LCD ,STB, Adapters
56
64
2.5
650
1.6
66
No
TO220F-6L
FSDM311
Aux Power, Adapters
12
20
0.55
650
19
70
No
DIP-8
FSDM311L
Aux Power, Adapters
12
20
0.55
650
19
70
No
LSOP-8
www.fairchildsemi.com/acdc 5
AC/DC Switch Mode Power Supply Design Guide
Pulse Width Modulator (PWM) Controllers Similarly to Green FPS, the FAN7601, FAN7602, and 7610 are green PWM controllers, offering burst mode operation during stand-by mode allowing the design to meet the International Energy Agency's (IEA) "1-Watt Initiative". • Burst mode operation • Operating frequency of up to 300kHz • Operating current 4mA (max) • Programmable soft start 20mS Burst Mode Operation Diagram VO
Burst mode operation: In order to minimize the power dissipation in standby mode, the Green PWMs implement burst mode functionality. As the load decreases, the feedback voltage decreases. As shown in the figure, the device automatically enters burst mode when the feedback voltage drops below VBURL. At this point switching stops and the output voltages start to drop at a rate dependent on standby current load. This causes the feedback voltage to rise. Once it passes VBURH switching starts again. The feedback voltage falls and the process repeats. Burst mode operation alternately enables and disables switching of the power MOSFET thereby reducing switching loss in standby mode.
VFH VBURH VBURL
Ids
Vds Time
PWM Controllers Part Number
Number of Outputs
Control Mode
Switching Frequency (kHz)
Supply Voltage Max (V)
Output Current Max (A)
Duty Ratio (%)
FAN7554
1
Current
500
FAN7601*
1
Current
300
FAN7602*
1
Current
FAN7610*
1
Current
KA3524
–
Voltage
KA3525A
2
Voltage
Startup Current (µA)
30
1
98
200
SO-8
20
0.25
98
Internal Switch
DIP-8, SO-8, SSOP-10
65
20
0.25
75
Internal Switch
DIP-8, SO-8, SSOP-10
QRC
20
0.5
–
Internal Switch
DIP-14, SO-14
350
40
0.1
–
8000
DIP-16
-
40
0.5
–
8000
DIP-16
Package
KA3842A
1
Current
500
30
1
100
200
DIP-8, SO-14
KA3842B
1
Current
500
30
1
100
450
DIP-8, SO-14
KA3843A
1
Current
500
30
1
100
200
DIP-8, SO-14
KA3843B
1
Current
500
30
1
100
450
DIP-8, SO-14
KA3844B
1
Current
500
30
1
50
450
DIP-8, SO-14
KA3845
1
Current
500
30
1
50
450
DIP-16
KA3846
2
Current
500
40
0.5
100
200
DIP-16
KA3882E
1
Current
500
30
1
100
200
SO-8
KA7500C
2
Voltage
300
42
0.25
–
1000
DIP-16, SO-16
KA7552A
1
Voltage
600
30
1.5
74
150
DIP-8
KA7553A
1
Voltage
600
30
1.5
49
150
DIP-8
KA7577
1
Voltage
208
31
0.5
53
150
DIP-16
ML4823
1
Voltage
1000
30
–
80
1100
DIP-16, SO-16
NOTE: FAN7602 and FAN7610 under development *Burst Mode Operation reduces system standby power to 1W or less
www.fairchildsemi.com/acdc 6
AC/DC Switch Mode Power Supply Design Guide
Power Factor Correction (PFC) Standalone and PFC/PWM Combo Controllers Fairchild’s full line of both stand alone PFC controllers and PFC/PWM combo controllers offer crucial cost-and energysaving solutions that address the demanding requirements of a diverse range of medium-and high-power Switch Mode Power Supply (SMPS) designs. • Offerings include both continuous/discontinuous devices • Current fed gain modulator for improved noise immunity • Synchronized clock output to reduce system noise and to synchronize to downstream converter • Patented one-pin voltage error amplifier with advanced input 180
9
8
160
8
7
140
120
6
120
6
100
5
100
5
80
4
80
4
3
60
3
40
2
40
2
20
1
20
0
0
0
60
VIN
IIN
7
VIN
1
IIN
Before Power Factor Corrected
Current
Voltage
140
Current
9 VCAP
160
Voltage
180
0
After Power Factor Corrected
Simplified Application Circuits DC VOUT
AC VIN
AC VIN
DC VOUT
FPS PFC
PFC/PWM Combo
PMW Optocoupler Reference
Optocoupler Reference
Stand-Alone PFC Controllers
PFC/PWM Combo Controllers
Power Factor Correction Stand-Alone Controllers Part Number
PFC Control
Operating Current (mA)
Startup Current (µA)
Package
FAN7527B
Discontinuous Mode
3
60
DIP-8, SOP-8
FAN7528
Discontinuous Mode
2.5
40
DIP-8, SOP-8
KA7524B
Discontinuous Mode
6
250
DIP-8, SOP-8
KA7525B
Discontinuous Mode
4
200
DIP-8, SOP-8
KA7526
Discontinuous Mode
4
300
DIP-8, SOP-8
ML4821
Average Current Mode
26
600
DIP-18, SOIC-20
FAN4810
Average Current Mode
5.5
200
DIP-16, SOIC-16
FAN4822
Average Current Mode
22
700
DIP-14, SOIC-16
Fpwm Over Fpfc
Operating Current (mA)
PWM Duty Cycle Max (%)
Power Factor Correction Combo Controllers Part Number FAN4800
PFC Control
Startup Current (µA)
Package
Average Current Mode
1
5.5
49
200
DIP-16, SOIC-16
FAN4803-1
Input Current Shaping Mode
1
2.5
50
200
DIP-8, SOIC-8
FAN4803-2
Input Current Shaping Mode
2
2.5
50
200
DIP-8, SOIC-8
ML4824-1
Average Current Mode
1
16
50
700
DIP-16, SOIC-16
ML4824-2
Average Current Mode
2
16
45
700
DIP-16, SOIC-16
ML4826
Average Current Mode
2
22
50
700
DIP-20
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AC/DC Switch Mode Power Supply Design Guide
Optocoupler Solutions The MICROCOUPLER™ package platform of optocouplers reduces board space and offers stable CTR up to 125°C, while offering high input to output isolation voltages. • High Current Transfer Ratio, CTR at low IF • Operating Temperature Range, Topr: -40°C to +125°C • Ultra small packaging – low profile 1.2mm • Applicable to Pb-free IR reflow soldering profile: 260°C peak
Normalized CTR @ 25°C
1.2 1 0.8 0.6 0.4
0 -40
BGA Package
MICROCOUPLER™ 4-Pin DIP Package
0.2
0
26
40
56
NOTE: under devlopement
70
110
90
125
Temperature (°C)
For a complete listing of Fairchild’s Optocouplers please visit: www.fairchildsemi.com/products/opto Optically Isolated Error Amplifiers Fairchild's FOD27XX series optically isolated error amplifiers offer designers a comprehensive selection of reference voltages, tolerances, isolation voltages and package sizes to optimize their specific power design.
Shunt Reference
FOD27XX
Transistor Optocoupler
FOD27XX VCC + _
=
To Primary
+
Comp From Secondary
NOTE: FOD2743 is a reverse pin-out
Optical Amplifiers Part Number
VREF (V)
Tolerance (%)
Isolation (kV)
Package
Operating Temperature (°C)
CTR* (%)
Bandwidth (kHz) 30
FOD2711
1.24
1
5.0
DIP-8
-40 to +85
100 – 200
FOD2741
2.5
0.5 – 2.0
5.0
DIP-8
-25 to +85
100 – 200
30
FOD2743
2.5
0.5 – 2.0
5.0
DIP-8
-25 to +85
50 – 100
50
* CTR is specified at ILED = 1mA
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AC/DC Switch Mode Power Supply Design Guide
Voltage References and Shunt Regulators Fairchild's suite of voltage references/shunt regulators offer flexible output voltages, space saving packages, and multiple voltage tolerances to meet the challenges of a SMPS design. • Programmable output voltages • Temperature compensated • Low output noise • Fast turn-on time Regulators Part Number
Preset Output Voltage (V)
Adj. Output Adj. Output Voltage (Min) (V) Voltage (Max) (V)
Tolerance (V)
Max Current (mA)
Package
FAN4041CI
Adjustable
1.22
12
0.5
30
SOT-23
FAN4041DI
Adjustable
1.22
12
1
30
SOT-23
FAN431
2.5 Adjustable
2.5
3
2
100
TO-92
KA431S
2.5 Adjustable
2.5
37
2
100
SOT-23F
LM336Bx5
5 Adjustable
4
6
2
15
TO-92
LM336x25
2.5
2.5
37
2
15
TO-92
LM336x5
5 Adjustable
4
6
4
15
TO-92
LM431A
2.5 Adjustable
2.5
37
2
100
SOIC-8, TO-92
LM431B
2.5 Adjustable
2.5
37
1
100
SOIC-8, TO-92
LM431C
2.5 Adjustable
2.5
37
0.5
100
SOIC-8, TO-92
LM431SA
2.5 Adjustable
2.5
37
2
100
SOT-23F, SOT-89
LM431SB
2.5 Adjustable
2.5
37
1
100
SOT-23F, SOT-89
LM431SC
2.5 Adjustable
2.5
37
0.5
100
SOT-23F, SOT-89
RC431A
Adjustable
1.24
12
1.5
20
SOT-23, TO-92
TL431A
2.5 Adjustable
2.5
37
1
100
SOIC-8, TO-92
TL431CP
2.5 Adjustable
2.5
37
2
100
DIP-8
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AC/DC Switch Mode Power Supply Design Guide
High Voltage Switching Technologies Fairchild offers an array of switching solutions for each application Switch QFET
IGBT
SMPS IGBT
SuperFET™
Higher
Switching Frequency
Lower
Lower
Wattage
Higher
Switch Mode Power Supply IGBTs Fairchild's SMPS IGBTs are optimized for switch mode power supply designs offering better VSAT/EOFF. Additionally, this control smooths the switching waveforms for less EMI. SMPS IGBTs are manufactured using stepper based technology which offers better control and repeatability of the top side structure, thereby providing tighter specifications. SMPS IGBTs vs. MOSFETs • Reduce conduction losses due to low saturation voltage • Reduce current tail, reduces switching losses • Improve transistor and system reliability • IGBT advantage in current density facilitates higher output power Reduce System Cost • Smaller die size for higher voltages reduces overall costs • May often eliminate components • Increase operating frequency and reduce transformer/filter cost • Fastest switching IGBTs in the market today Stealth™ Diode Co-Pack Diode Recovery Comparative Data
• Avalanche energy rated • Offers soft recovery switching (S = tb/ta>1) at rated current, high
TJ = 125°C, IF = 13.5A, di/dt = 90A/µs, VR = 400V
switching di/dt, and hot junction temperature (125°C) charge (QRR) and reduced Irrm
Current
Irrm (Stealth)
• Maximize IGBTs efficiency with the improved lower reverse recovery
0 VCE = 100V/div
• Reduces switching transistor turn-on losses in hard switched applications • Reduces EMI
Irrm (Competitor) ICE = 5A/div
• Offers reverse recovery times (trr) as low as 25ns – superior to fast Time = 25ns/div
recovery diode MOSFETs • Elimination of snubber circuit becomes possible
• Improved device efficiency with the improved lower reverse recovery charge (QRR) and reduced Irrm • Reduces switching transistor turn-on losses in hard switched applications
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AC/DC Switch Mode Power Supply Design Guide
High-Voltage MOSFETs SuperFET and QFET technologies are high voltage MOSFETs from Fairchild with outstanding low on-resistance and low gate charge performance, a result of proprietary technology utilizing advanced charge balance mechanisms. • Ultra-low RDS(ON) (0.32Ω), typical Packages
• Best-in-class di/dt (1430A/µs, max) • Low output capacitance (Coss = 35pF, typical)
TO-3P
Fairchild MOSFET Technology Comparison
FOM (FOM = RDS(on) x Qg)
50 D2-PAK
45
FQP8N60C RDS(ON) 0.975 Qg 27.0 nC
40 35 30 25 20 15 10
FQP7N60 R DS(ON) 0.80 Ω Qg 29.0 nC
FQP5N50C RDS(ON) 1.072 Ω 18.0 nC Qg FQP19N20C RDS(ON) 0.135 Ω 40.5 nC Qg
FQP11N40C RDS(ON) 0.43 Ω 28.0 nC Qg
FQP19N20 R DS(ON) 0.12 Ω Qg 31.0 nC
FQP11N40 RDS(ON) 0.38 Ω Qg 27.0 nC
FQP7N80 RDS(ON) 1.20 Qg 40.0 nC FQP7N80C RDS(ON) 1.59 Ω 27.0 nC Qg
FQP5N50 RDS(ON) 1.36 Ω Qg 13.0 nC
D-PAK
TO-126
TO-247
FQP18N20V2 R DS(ON) 0.12 Ω Qg 20.0 nC
QFET QFET C-series
FCP11N60 R DS(ON) 0.32 Ω 40.0 nC Qg
FQP18N50V2 R DS(ON) 0.23 Ω Qg 42.0 nC
5
QFET V2-series SuperFET
TO-92
0 200
400
500
600
800 TO-220
Voltage MOSFET Selection Table VDSS Specification 200V RDS(ON), typ (Ω) RDS(ON), max (Ω)
8-SOP QFET™
C-Series
V2-Series
FQP19N20
FQP19N20C
FQP18N20V2
0.12
0.135
0.12
SuperFET™
–
0.15
0.017
0.14
–
Qg, typ (nC)
31.00
40.50
20.00
–
Qgd, typ (nC)
13.50
22.50
10.00
–
–
400V
FQP11N20
FQP11N40C
RDS(ON), typ (Ω)
0.38
0.43
–
–
RDS(ON), max (Ω)
0.48
0.53
–
–
Qg, typ (nC)
27.00
28.00
–
–
Qgd, typ (nC)
12.30
15.00
–
–
FQP5N50
FQP5N50C
FQP18N50V2
RDS(ON), typ (Ω)
1.36
1.072
0.23
–
RDS(ON), max (Ω)
1.80
1.40
0.265
–
13.00
18.00
42.00
–
500V
Qg, typ (nC) Qgd, typ (nC)
6.40
9.70
14.00
–
FQP7N60
FQP8N60C
–
FCP11N60
RDS(ON), typ (Ω)
0.8
0.975
–
0.32
600V RDS(ON), max (Ω)
1.00Ω
1.2Ω
–
0.38
Qg, typ (nC)
29.00
28.00
–
40.00
Qgd, typ (nC)
14.50
12.00
–
21.00
–
800V
FQP7N80
FQP7N80C
–
RDS(ON), typ (Ω)
1.2
1.59
–
–
RDS(ON), max (Ω)
1.5
1.9
–
–
Qg, typ (nC)
40.00
27.00
–
–
Qgd, typ (nC)
20.00
10.60
–
–
www.fairchildsemi.com/acdc 11
TO-3PF
I2-PAK
I-PAK
8-DIP
TO-264
TO-92L
TO-220F
SOT-223
AC/DC Switch Mode Power Supply Design Guide
Additional Discrete Components Fairchild is a leading supplier of discrete components providing a broad portfolio in an array of packages and functions to meet each design need, including: Discrete BGA Packaging
• Low-voltage MOSFETs • Low-voltage MOSFET and Schottky combos • Diodes and rectifiers – Schottky – Bridge
Discrete FLMP Packaging
– Small signal – Zener • Bipolar transistors and JFETs
Low-voltage MOSFET BGAs combine small footprint, low profile, low RDS(ON), and low thermal resistance to effectively address the needs of space-sensitive, performance-oriented load management and power conversion applications. For additional information on Fairchild’s BGA packaging and product selection, visit www.fairchildsemi/products/ discrete/power_bga.html Fairchild’s patented FLMP packaging eliminates conventional wire-bonds and also provides an extremely low thermal resistance path between the PCB and the MOSFET die (drain connection). This can greatly improve performance compared to many other MOSFET packages by reducing both the electrical and the thermal constraints. For additional information on Fairchild’s FLMP packaging and product selection, visit www.fairchildsemi/products/discrete/flmp.html Package Impedance Comparisons Package Description
Ldd (nH)
Lss (nH)
Lgg (nH)
Rd (mΩ)
Rs (mΩ)
Rg (mΩ)
2 x 2.5mm BGA
0.056
0.011
0.032
0.05
0.16
0.79
4 x 3.5mm BGA
0.064
0.006
0.034
0.02
0.06
0.95
5 x 5.5mm BGA
0.048
0.006
0.041
0.01
0.04
0.78
FLMP (Large 3s)
0.000
0.744
0.943
0.002
0.245
2.046
FLMP (Large 7s)
0.000
0.194
0.921
0.002
0.137
2.038
SO-8
0.457
0.901
1.849
0.12
2.04
20.15 1.77
SO-8 Wireless
0.601
0.709
0.932
0.16
0.23
IPAK (TO-251)
2.920
3.490
4.630
0.25
0.74
8.18
DPAK (TO-252)
0.026
3.730
4.870
0.00
0.77
8.21
D2PAK (TO-263)
0.000
7.760
9.840
0.00
0.96
12.59
www.fairchildsemi.com/acdc 12
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 1W Power Supply with less than 100mW Standby Power using FSD210 Typical Application – Small home or factory automation appliances Lp = 1200µH 94/9/2 EF13 (on Vogt Fi324 core) T1 EF13 VOGT 6PIN
L100
1
D103 P6KE150A Pm = 600W
D101 1N4007
FS1 230V/250mA
9V/100mA output
6
D201 1 2 3 4
5 3
4
EGP10D
CONN2 B4B-XH-A
D102 UF4007
5
R105 10R 0.125W
VCC
DRAIN
7
D105
VSTR
+ C101 10µF 400V
8
+ C100 10µF 400V
R100
FDLL4148
D202 BZX84C9 0.35W
+ C201 220µF 25V
VFB
R201 100R 0.125W
fsw=134kHz
4
GND
GND 3
2
1
GND
IC1 FSD210M
1
2
R101
L101
+ C104 47µF 50V
C103 4.7µF 63V
Q1 BC847B
R202 470R 0.125W
CONN1 B2P3-VH
85V-265VAC input
This compact non-isolated flyback solution draws less than 100mW standby power over the whole input voltage range. This example shows a 9V output system. Here the FSD210 is powered from an auxiliary winding rather than directly from the high voltage bus. For output voltages of 12V and over, the device may be powered directly from the output winding. A low cost Zener diode circuit provides the regulation reference. • Less than 100mW standby power – Ideal for applications permanently connected to an AC supply • Overload protection circuit distinguishes between temporary and permanent overload – Device does not shut down during load surge conditions – Inherent short circuit protection • Frequency modulation reduces EMI reduction circuitry – Low cost, compact solution possible Fairchild Devices FSD210M P6KE150A EGP10D BZX84C9 UF4007 1N4007 FDLL4148 BC847B
Description Fairchild Power Switch (0.3A/134kHz) Transient Voltage Suppressor (600W/150V) Fast Recovery Diode (1A/200V) Zener Diode (9V) Fast Recovery Diode (1A/1000V) General Purpose Diode (1A/1000V) General Purpose Diode (10mA/100V) General Purpose Transistor
www.fairchildsemi.com/acdc 13
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits Dual Negative Output Non-Isolated Flyback using FSD200 Typical Application – Home appliance control board power supply Lp = 1500µH 100/11/10 EF13 (on Vogt Fi324 core) T1 EF13 VOGT 6PIN
L100 FS1 230V/250mA
1
D101 D100 1N4007 1N4007
D103 P6KE150A
6
D211 EGP10D
-5V/300mA, -12V/100mA output 3 2 1
5 3
D201 EGP10D
Pin 3: Mains Ground Pin 2: -5V/300mA Pin 1: -12V/100mA
5
7
VCC
DRAIN
VSTR
D202 BZX84C5V1 0.35W
VFB
fsw = 134kHz
Q1 BC847B
4
GND 3
GND 2
1
GND
IC1 FSD200M
D106 FDLL4148
1
2
R101
L101
C103 47nF 63V
+ C104 1µF 50V
R201 100R 0.125W
+
+ C101 10µF 400V
C201 220µF 25V
+
+ C100 10µF 400V
8
D102 UF4007
R100
CONN2 B3P-VH
4
C211 220µF 25V
R202 470R 0.125W
CONN1 B2P3-VH
85V-265VAC from appliance input filter stage
A dual non-isolated flyback is used to generate voltages which are negative with respect to the neutral power line. This is used in applications where triacs are driven, such as in household appliances. A Zener diode, a bipolar transistor and a diode allow the negative voltage to be regulated by the FPS. The dual input diode helps to protect against line transients. • Generation of two negative outputs referred to the input line – Useful for applications using triacs • High switching frequency reduces the required inductance – More compact, lower cost core • Frequency modulation reduces EMI reduction circuitry – Split 400V input capacitor and input inductor sufficient in most cases Fairchild Devices FSD200M P6KE150A EGP10D BZX84C5V1 UF4007 1N4007 FDLL4148 BC847B
Description Fairchild Power Switch (0.3A/134kHz) Transient Voltage Suppressor (600W/150V) Fast Recovery Diode (1A/200V) Zener Diode (5.1V) Fast Recovery Diode (1A/1000V) General Purpose Diode (1A/1000V) General Purpose Diode (10mA/100V) General Purpose Transistor
www.fairchildsemi.com/acdc 14
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 10W Single Output Isolated Flyback using FSDM0265RN and Zener Diode Typical Application – Power bricks and single-phase frequency inverters
Lp = 2400µH 114/9/4 EF20 (on Vogt Fi324) C300 Y1
FS101 230V/3A
T1 VOGT EF20
L100 D101 1N4007
R102 100k 2W
C103 2.2nF 1000V
4
8
3
6
L201 2.7µH
2
D102 1N4007
1
R101 D103 1N4007
85V-265VAC input
7
6 Drain
8 VStr
GND
5
Drain
Drain
1
+ C102 22µF 400V
Vcc
Ipk
+ C101 22µF 400V
2
VFB
+ C201 220µF 50V
R103 10R 0.6W
IC1 FSDM0265RN fsw = 70kHz
+ C202 220µF 50V
1 2 3 4
5V/2A output D202 BZX84C3V9 0.5W
D106 1N4148
2 3
C105 1µF 50V
4
CONN101 B2P3-VH
1
D105 UF4007
CONN201 B4P-VH
D201 SB540
R104 4.7K 0.6W
L101
C104 100nF 50V
IC2 H11A817A.W 4
1
3
2
R201 120R 0.6W
D104 1N4007
The FSDM0265RN contains a PWM controller and a MOSFET on two different chips. The 650V MOSFET is fully avalanche rated and tested which leads to increased system reliability. This application shows a cost reduced feedback circuit using a Zener diode. R104 is used to reduce the current limit. Higher power parts in the green FPS family have a higher current limit and a lower RDS(ON) than the lower power parts. Using a lower RDS(ON) part increases the efficiency, particularly at low input voltages. So replacing a low power part with a high power part increases the efficiency but also the current limit. If it were not possible to reduce the current limit, the flyback transformer would have to be rated at the higher current limit, making it more expensive. • FSDM0265RN has a fully avalanche rated MOSFET – Robust performance under transient conditions • Overload protection circuit distinguishes between temporary and permanent overload – Device does not shut down during load surge conditions – Inherent short circuit protection • Current limit may be lowered using an external resistor – Increased flexibility in choice of range of FPS parts Fairchild Devices FSDM0265RN BZX84C3V9 H11A817A SB540 UF4007 1N4007 1N4148
Description Fairchild Power Switch (1.5A/70kHz) Zener Diode (3.9V) Transistor Optocoupler Schottky Diode (5A/40V) Fast Recovery Diode (1A/1000V) General Purpose Diode (1A/1000V) General Purpose Diode (10mA/100V)
www.fairchildsemi.com/acdc 15
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 10W Multiple Output Isolated Flyback using FSD210 with Primary Side Regulation Typical Application – Set top boxes, decoders and small DVD players Lp = 2200µH EF20 (on Epcos N67 core)
FS1 230V/1A
TR1
0
8 12
R1
D2 1N4007
D3 P6KE200
100R
11
D5 BA159
D6 1N4007
D8 1N4148
FL1/VFD
1
-22V/50mA
2
5
7
4 9
C8 1µF 50V D12 10V 0.5W
C10 33nF 50V
1
2
D15 1N4007
C11 22nF 50V
Q4 BC546B
D4 1N4935
5
-12VA/50mA R11 560R
Primary 81 turns Vcc 7 turns 5V 3 turns 3.3V 2 turns 12V 9 turns 22V 11 turns VFD 2 turns
R10 120R
R101
R2 100R + C2 22µF 35V
EF20 EPCOS 12Pin
D14 1N4007 L2 2.2mH 0.09A
0
C5 10µF 50V
D17 12V
C14 100nF 50V
C15 10µF 16V
6
D9 1N4148
Vcc VFB
4
GND
3
8 VSTR
1
DRAIN
+
GND
C7 4.7µF 400V
GND
+
2
C6 4.7µF 400V
D10 1N4935
0 10
fsw = 134kHz IC1 FSD210M
FL2/VFD
7
3
R3 68R
D1 1N4935
+
L1 2.2mH 0.09A
+
C1 2.2nF Y1
0
0
+12VA/50mA +12V/50mA C3 100nF 50V
D7 12V
+ C4 10µF 16V
0 +3.3V/0.5A
D13 SB140
+ C9 100µF 16V 0 L3
FERRITE BEAD +5V/0.5A
D16 SB140
+ C12 100µF 16V
+ C13 100µF 16V
10W output
0
PL3 B2P3-VH
195V-265VAC input
Multiple output flyback converters are used in applications where power is supplied to diverse sub-systems such as drives, tuners, audio stages and complex processor and logic circuits. Primary side regulation is used in this circuit to reduce the total cost. For this power level and above it is more cost effective to use four diodes in a full bridge configuration than a single diode with a larger capacitor. For high current outputs it is recommended to use a Schottky diode on the secondary side. • Primary side regulation reduces system cost – Cross regulation is good, total regulation worse than with an optocoupler solution • Frequency modulation approach minimizes EMI circuitry – Common-mode choke can be replaced by a simple dual capacitor, dual low cost inductor circuit • Overload protection circuit distinguishes between temporary and permanent overload – Device does not shut down during load surge conditions from drive unit – Inherent short circuit protection Fairchild Devices FSD210M BZX84Cxx P6KE200 SB140 1N4935 1N4937 UF4007 1N4007 1N4148 BC546B
Description Fairchild Power Switch (0.3A/134kHz) Zener Diodes (10V, 12V) Transient Voltage Suppressor (600W/200V) Schottky Diode (1A/40V) Fast Recovery Diode (1A/200V) Fast Recovery Diode (1A/600V) Fast Recovery Diode (1A/1000V) General Purpose Diode (1A/1000V) General Purpose Diode (10mA/100V) General Purpose Transistor
www.fairchildsemi.com/acdc 16
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 2.5W Single Output Isolated Flyback using FSD200 with KA431 Reference Typical Application – Isolated main or standby power supplies for household appliances
Lp = 2400µH 114/9/4 EF20 (on Vogt Fi324) C300 Y1
FS101 230V/3A
T1 VOGT EF20
L100 D101 1N4007
R102 100k 2W
C103 2.2nF 1000V
4
8
3
6
L201 2.7µH
2
D102 1N4007
1
R101 D103 1N4007
85V-265VAC input
6
7
VStr GND
5
Drain
8 Drain
1
Drain
2
+ C102 22µF 400V
Vcc Ipk
+ C101 22µF 400V
VFB
+ C201 220µF 50V
R103 10R 0.6W
IC1 FSDM0265RN fsw = 70kHz
+ C202 220µF 50V
1 2 3 4
5V/2A output D202 BZX84C3V9 0.5W
D106 1N4148
2 3
C105 1µF 50V
4
CONN101 B2P3-VH
1
D105 UF4007
CONN201 B4P-VH
D201 SB540
R104 4.7K 0.6W
L101
C104 100nF 50V
IC2 H11A817A.W 4
1
3
2
R201 120R 0.6W
D104 1N4007
In this converter, isolation is provided by the transformer and the H11A817A optocoupler. Output accuracy is improved using the KA431 voltage reference. The values R201, R203, C206, R204 and C104 set the closed loop control parameters and performance. Using a Schottky diode is a cost-effective method of improving efficiency where needed. • Feedback circuit using KA431 reference and H11A817A optocoupler – More accurate regulation over line, load and temperature than with a Zener diode • Schottky diode used in output stage – Cost-effective means of improving efficiency • Integrated soft start function – Prevents power surges during switch-on time Fairchild Devices FSD200M KA431 H11A817A SB180 UF4007 1N4007
Description Fairchild Power Switch (0.3A/134kHz) 2.5V Reference (2.5V) Transistor Optocoupler Schottky Diode (1A/80V) Fast Recovery Diode (1A/1000V) General Purpose Diode (1A/1000V)
www.fairchildsemi.com/acdc 17
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 180W-200W Quasi-Resonant Flyback with Input Power Factor Correction using KA5Q1265RF, FAN7527B, and FQP13N50C Typical Application – Color Televisions NTC100 2R
11
14 3
C114 630V
R302 20K 0.25W
C309 1nF 25V
R110 S10K275
Q301 FQP13N50C
FAN7527B
R306 10R 0.25W
+ C201 1000µF 50V
C210 470pF 1000V + C101 220µF 450V
R309 6K 0.25W
R307 0.3R 0.6W
D211 EGP20D
D304 8V2 0.5W
VR301 10K
18V/1A + C212 1000µF 50V
+ C211 1000µF 50V
CONN2 B9P-VH L221 10µH 5A
D221 FYPF0545
Lp = 530µH Np/Ns = 0.8
45V/0.01A + C202 1000µF 50V
L211 10µH 5A
C220 470pF 1000V
D303 1N4148
LF100
L201 10µH 5A
D201 EGP20D
R318 470K 0.25W
C307 1µF MLCC 50V
R305 22K 0.6W 4 3 2 1
-
BD100
R311 1M 0.25W
C113 630V
C200 470pF 1000V R308 470K 0.25W
5 6 7 8
+
12V/2A + C222 1000µF 50V
+ C221 1000µF 50V
1 2 3 4 5 6 7 8 9
T1 EF42 VOGT
D103 1N4937
1
22 21
C110 250V
D108 1N4007
R108 68K 0.5W
R118 68K 0.5W
20
3
19 18
C230 470pF 1000V
17
R103 10R 0.25W
FS1 230V/3A
7
16
9
15
D231 EGP20K
1
D10 1N49376
Sync
Vcc
C104 47nF 50V
5
GND
FB 4
3
Drain
C107 680pF 1600V +
2
1
C103 47µF 50V
D241 FYPF0545
D105 1N4937
C105 3.3nF 50V
R105 470R 0.25W
IC2 H11A817A 4
1
3
2
R201 1K 0.25W
C400 R204
IC3 KA431LZ
+ C232 100µF 200V
+ C241 1000µF 50V
CONN3 B2P-VH 1 2
8.5V/1A + C242 1000µF 50V
180W-200W Output
R204 250K 0.25W
R202 1K 0.25W R203
140V/0.9A
L241 10µH 5A
R106 600R 0.25W
F
195V-265VAC input
+ C231 100µF 200V
C240 470pF 1000V
IC1 KA5Q1265RFYDTU
CONN1 B2P3-VH
L231 10µH 5A
14 13
BEAD101 FERRITE BEAD 2
C112 630V
T301 VOGT EF25 PFC 6
R301 1M2 0.25W
C305 470nF 630V C111 630V
D302 EGP30J
Lp = 600µH, 3A, 58T/4T EF25 (on Vogt Fi324 core)
C206
39K 100nF 0.25W 100V
High/Low VR201 30K R206 4K7 0.25W
www.fairchildsemi.com/acdc 18
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 180W-200W Quasi-Resonant Flyback with Input Power Factor Correction using KA5Q1265RF, FAN7527B, and FQP13N50C (Continued) Typical Application – Color Televisions The circuit shown consists of a PFC stage built around the FAN7527B/FQP13N50C/EGP30J circuit and the quasi-resonant PWM stage built around the KA5Q1265RF/T1 circuit. This circuit is suited for input voltages in the range from around 195V to 265V. The transition mode PFC stage generates a DC bus voltage of around 400V. The purpose of the stage is to reduce the harmonic content of the input current drawn from the AC supply as required by the EN61000-3-2 standard. An additional benefit is that the input power factor is very high. The KA5Q1265RF circuit generates the required output voltages using a multiple output flyback configuration. The device operates in discontinuous mode and detects the point where the secondary current has dropped to zero. The device then switches on after a delay set by the circuit around C105. As the delay is chosen to be at the first minimum of the primary side voltage ring as it changes from Vin + nVo to Vin - nVo the device is switched on at a low voltage, which reduces the switching loss. The switching frequency is therefore asynchronous and varies with the load. This reduces the visible effect of switching noise on the television screen. Fixed frequency switching noise would be seen as diagonal lines on the screen. The turns ratio is chosen to be unusually low for a standard flyback because the output voltage on the main winding is exceptionally high. This keeps the reflected voltage nVo low. If the load on a quasi-resonant flyback circuit is reduced, the switching frequency increases which causes a reduction in efficiency. The KA5Q series has a burst mode of operation. In normal operation the High/Low signal is High. When this signal which is typically supplied by a microcontroller is Low, the current increases through the optocoupler, the feedback voltage goes to ground and the device enters burst mode. In this case the output voltages drop until the voltage supplied to the chip through the auxiliary winding drops to around 12V. The device remains in hysteretic burst mode until the feedback voltage increases. In this low power mode, the PFC chip is deactivated via D304. In normal operation, the auxiliary winding voltage is around 24V, so there is sufficient voltage to power up the PFC chip. In burst mode, the FPS voltage is between 11V and 12V, so the FAN7527B chip is deactivated, as its supply voltage is around 8V lower than this. • Complete PFC and PWM solution for a color television power supply – High efficiency (typically 90% at full load) – High power factor and low input current harmonics • Quasi-resonant mode ideal for TV applications – High efficiency due to lower voltage switching – Asynchronous switching is not at constant frequency – Slower dV/dt causes lower internal radiated interference • Supports low power standby – Hysteretic burst mode for KA5Q1265RF device – FAN7527B PFC controller deactivated at low power Fairchild Devices KA5Q1265RF FAN7527B FQP13N50C EGP30J 1N4937 GBU4M BZX85C8V2
Description Fairchild Power Switch (8A/quasi resonant) Transition mode PFC controller High Voltage MOSFET (13A/500V) Fast Recovery Diode (3A/600V) Fast Recovery Diode (1A/600V) Bridge Rectifier (4A/1000V) Zener Diode (8.2V)
Fairchild Devices KA431 H11A817A EGP20D EGP20K FYPF0545 1N4007 1N4148
www.fairchildsemi.com/acdc 19
Description 2.5V Reference (2.5V) Transistor Optocoupler Fast Recovery Diode (1A/200V) Fast Recovery Diode (1A/600V) Fast Recovery Diode (5A/45V) Fast Recovery Diode (1A/1000V) General Purpose Diode (10mA/100V)
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 16W Multiple Output Isolated Flyback Converter using FSDM0265RN Typical Application – Set top boxes, decoders, and small DVD players Industrial and communications applications using FPGAs and complex logic chips Lp = 1000µH EF25 (on Vogt Fi324 core)
T1 1 6
8
D102 UF4007 5
R103 22R 0.6W
DF10M BR101
10
R105 2.2k 0.6W
0V
IC2 H11A817A 4 3
+ C103 10µF 50V
2
2
1
85V-265VAC input
L4 56µH
0V
C104 33µF 50V
Primary 80 turns Vcc 14 turns 5V 6 turns 3.3V 4 turns 6.6V 8 turns 12V 14 turns
3
C300 250V
C9 100nF 63V
0V
3
R202 1K 0.6W
2
1
2
2.5V C5 100nF 63V
0V
0V
VIN
VOUT
0V
0V R201 220R 0.6W
VOUT
3.3V/1.2A (incl 1.2V load)
+ C14 220µF 16V IC4 0V FAN1112D
+ C16 2200µF 16V 0V
D13 SB330
CONN1 B2P3-VH
VIN
C2 100nF 63V
C110 275V
FS1 230V/3A
0V IC5 FAN1616AS25
1 3
3
5V/1.2A (incl 2.5V load)
+ C11 220µF 16V
+ C12 2200µF 16V
D12 SB360
1
7
6
VFB
2
L3 56µH
0V
2
1.2V C10 100nF 63V
1
1
IC1 FSDM0265RN
Vcc
6.6V/0.7A
+ C7 1000µF 16V
D14 SB360
4
D103 1N4148
Drain
8
VStr GND
5
Drain
Drain
R110
T3
0V
9
0V
ILim
~ -
+ C101 47µF 400V
4
~ +
12V/100mA + C15 47µF 25V
D15 SB180
7
GND
3
GND
C102 10nF 1000V
R102 10k 2W
R204 1.2K 0.6W
C206 100nF 100V
R203 2.2K 0.6W
0V
16W output
R205 5.6K 0.6W
IC3 KA431LZ 0V
The isolated, multiple output application shown is suited to applications requiring all of the common logic supply voltages: 5V, 3.3V, 2.5V and 1.2V. The flyback architecture is easily expandable: two additional outputs at 12V and 6.6V are shown in this application. The design is scalable to higher power levels by changing the size of the FPS device and the transformer. The FSDM0265RN uses current mode control which provides excellent response to line and load transient conditions. The flexible overload protection can distinguish between a temporary current surge and a longer term overload condition. The over current latch is a current limit which is active even during the blanking time. This provides additional system robustness against a secondary diode short circuit condition. • FSDM0265RN has a fully avalanche rated MOSFET with overcurrent latch – Robust performance under transient conditions – Device switches off if there is a secondary diode short • Overload protection circuit distinguishes between temporary and permanent overload – Device does not shut down during load surge conditions – Inherent short circuit protection • Current limit may be lowered using an external resistor – Increased flexibility in choice of range of FPS parts Fairchild Devices FSDM0265RN FAN1112D FAN1616AS25 H11A817A KA431 DF10M
Description Fairchild Power Switch (1.5A/70kHz) Voltage Regulator (1.2V/1A) Voltage Regulator (2.5A/0.5A) Transistor Optocoupler 2.5V Reference (2.5V) Bridge Rectifier
Fairchild Devices SB180 SB330 SB360 UF4007 1N4148
Description Schottky Diode (1A/80V) Schottky Diode (3A/30V) Schottky Diode (3A/60V) Fast Recovery Diode (1A/1000V) General Purpose Diode (10mA/100V)
www.fairchildsemi.com/acdc 20
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 40W Isolated Flyback Power Supply using FSDM07652R Typical Application – AC Input Industrial Control, LCD Monitor
Lp = 520µH EER3016 T1:EER 3016 DB101 2KBP06
+ 2
1
1
3
+ C103 100µF 400V
R102 40K 1W
C104 100µF 400V
D201 MBRF10100
12V C201 1000µF 25V
R206 56K 2W
L201
10
+ C202 1000µF 25V
+
8
2
4-
2
R105 40K 1W
D101 UF4007
40W output 3
C102
R104 5R
220nF 275VAC
6 5 4
LF101:23mH
3
R101
C101
ZD101 22V
220nF 275VAC
2
Vstr Drain NC GND
4
1 5
2
+ C105 22µF 50V
F101 FUSE
1
L202
7
5V C203 1000µF 10V
C204 1000µF 10V
+
+
6
Vfb
C301
Vcc
IC101 FSDM07652R
560K/1W
RT101
D202 MBRF1045
D102 1N4148
4.7nF YCAP
C106 47nF 50V
R201 1K
IC301 H11A817A
Primary 36 turns Vcc 8 turns 5V 3 turns 12V 7 turns
R204 5.6K
R202 1.2K
R203 10K
C205
47nF 50V IC201 KA431
R205 5.6K
85V-265VAC Input
CONN1 B2P3-VH
This shows a higher power isolated flyback application, sharing the same features as many of the lower power applications. A lower inductance value is used to ensure that the associated leakage inductance is also kept low in this application, remembering that snubber losses are proportional to the leakage inductance and to the square of the current. • FPS containing PWM IC with co-packaged MOSFET solution is very robust and improves system reliability – Fully avalanche rated switch – Over current protection for secondary diode short circuit – Over voltage protection • Current mode control gives excellent line and load regulation – Better regulation • Overload protection distinguishes between temporary and permanent overload • Internal soft start reduces inrush current and output overshoot on turn on Fairchild Devices FSDM07652R H11A817A KA431 1N4007 1N4148 KBP06M
Description Fairchild Power Switch (2.5A/70kHz) Optocoupler 2.5V Reference (2.5V) General Purpose Diode (1A/1000V) General Purpose Diode (10mA/100V) Bridge Rectifier Diode (1.5A/600V)
www.fairchildsemi.com/acdc 21
AC/DC Switch Mode Power Supply Design Guide
Examples of Typical Application Circuits 24W Flyback Converter using 1500V IGBT and FAN7554 Typical Application – Motor Drives, Uninterruptible Power Supplies, 3-Phase Input Systems
D1
D2
D3
1N4007
1N4007
1N4007
R102 33k 1W
R121 150k 1W
C102 10nF 1000V
UF4007
R122 150k 1W
4
+
C203 1000µF 50V
D202 EGP20D
2 3
R126 4.7K 0.25W
R105 110k 0.6W
+
C202 220µF 50V
CONN2 B2P-VH 1 2
R103 10R 0.6W
Q1 SGF5N150UFTU
EF35
R206 0R 0.6W
CONN3 B2P-VH
R207 N.C. 0.6W
1 2
D103
5
6
R201 1K8 0.6W
GND
R123 10K 0.25W
OUT
VREF
C206 100nF 25V
RT/CT
R203 39K 0.6W
4
1
R107 110k 0.6W
R205 1K5 0.6W
IC2 H11A817A.W
+
C122 1µF 50V
C123 1nF 25V
R127 330 0.25W
R128 0.8R 2W
C104 47nF 63V
4
1
3
2
IC3
3
C21 5.6nF 25V
R204 13K 0.6W
R202 1K8 0.6W
IC1 FAN7554
+
IS
+ C103 22µF 50V
7
1N4148
FB
C106 47µF 400V
C201 1000µF 50V
10 9 8
1
+
R106 110k 0.6W
+
7
R125 22 0.25W
8
C105 47µF 400V
R104 110k 0.6W
3
1N4007
VCC
D6
1N4007
SS
D5
1N4007
24V/1A output
L201 22µH
14 13 12
6
2
D4
D201 EGP20D
T1 1
D102
1
KA431LZ
2
Note: EMI components removed from circuit for clarity
1 2 3 4
3 phase input
CONN1 B4P-VH
This inventive flyback solution uses a cost-effective 1500V IGBT as the main switching element, offering a more robust design. The alternative option for the switch would be a MOSFET with a rated voltage exceeding 1000V, which is a more expensive solution. The FAN7554 PWM controller provides the PWM regulation. Frequency compensation comes from the standard KA431 reference circuit. • Flyback converter with cost-effective 1500V IGBT – Ensures high robustness against external voltage transients at a reasonable cost • Complete, tested sub-system solution from Fairchild's Global Power Resource with test circuit data – Fairchild Semiconductor offers all semiconductor components in the circuit – Efficiency exceeds 78% for 24W output, 600V input, 20kHz switching frequency – Efficiency exceeds 74% for 24W output, 600V input 40kHz switching frequency – IGBT temperature rises less than 40°C in test circuit Fairchild Devices SGF5N150UFTU FAN7554 EGP20D H11A817A.W KA431LZ 1N4007 UF4007 1N4148
Description 1500V, 5A IGBT PWM Controller Fast Recovery Diode (1A/200V) Transistor Optocoupler 2.5V Reference (2.5V) Diode (1A/1000V) Fast Recovery Diode (1A/1000V) General Purpose Diode (10mA/100V
www.fairchildsemi.com/acdc 22
AC/DC Switch Mode Power Supply Design Guide
Design Ideas 250W to 450W Desktop PC Forward Switch Mode Power Supply Boost Diode
Rectifier
PFC (Power Factor Correction)
Transformer
PWM (Pulse Width Modulator)
Optocoupler
Suggested Products Bridge Rectifier 2KBP10M
PFC IC ML4821
PFC MOSFET FCP20N60
Boost Diode
PWM IC
FFP05U60DN
KA384X KA3525
PWM MOSFET FQP8N80C
Rectifier
H11A817 MOC819
GBU4M
FAN4810
FQP18N50V2
RHRP860
FQP9N90C
12V FFPF10U20DN
GBU6M
FAN4822
FDH27N50
FFP10U60DN
FQA10N80C
12V FFAF10U20DN
FCP11N60
IRL9R860
FQA11N90
KBL10
5V FYAF3004DN 3.3V FYP1504DN 3.3V FYP2004DN 3.3V FYAF3004DN
www.fairchildsemi.com/acdc 23
Optocoupler
12V FPF06U20DN
AC/DC Switch Mode Power Supply Design Guide
Design Ideas 500W Telecom/Server Double Switch Forward Switch Mode Power Supply Boost Diode
PWM MOSFET
Synch. Rectifier PFC (Power Factor Correction)
PFC MOSFET Synch. Rectifier PWM MOSFET
Optocoupler
Suggested Products Bridge Rectifier 2KBP10M
PFC IC ML4821
PFC MOSFET FQA24N50
Boost Diode ISL9R860
PWM MOSFET
Synch. Rectifier
FQH18NH50V2
FDP060AN08A0
H11A817 MOC819
GBU4M
FAN4810
FCP11N60
IRL9R1560
FQA24N50
FDP047AN08A0
GBU6M
FAN4822
FDH44N50
RHRP860
FQH27N50
FDP3652
FQH44N50
FDP3632
KBL10
RHRP1560
FCP11N60
Optocoupler
FQP90N10V2
FCP20N60
www.fairchildsemi.com/acdc 24
AC/DC Switch Mode Power Supply Design Guide
Design Ideas 500W Telecom/Server ZVS Phase-Shift Full Bridge Switch Mode Power Supply Boost Diode
PWM MOSFET
Synch. Rectifier PFC (Power Factor Correction)
PFC MOSFET Synch. Rectifier PWM MOSFET
Optocoupler
Suggested Products Bridge Rectifier 2KBP10M
PFC IC ML4821
PFC MOSFET FQA24N50
Boost Diode
PWM MOSFET
ISL9R860
FQH18N50V2
Synch. Rectifier
H11A817 MOC819
GBU4M
FAN4810
FCP11N60
IRL9R1560
FQA24N50
FDP047AN08A0
GBU6M
FAN4822
FCP20N60
RHRP860
FDH27N50
FDP3652
FDH44N50
RHRP1560
FDH44N50
FDP3632
FCP11N60
FQP90N10V2
KBL10
FCP20N60
www.fairchildsemi.com/acdc 25
Optocoupler
FDP060AN08A0
AC/DC Switch Mode Power Supply Design Guide
Application Note Highlight
Design Guidelines for Off-Line Flyback Converters using Fairchild Power Switch (FPS™) (AN-4137) Introduction Designing a switched mode power supply (SMPS) is a complex process with many variables and considerations. While most power supply design engineers have developed their own methods, here is an overview describing the design of a flyback converter using Fairchild FPS devices. For a more detailed explanation of this procedure, refer to Application Note AN-4137, Design Guidelines for Off-line Flyback Converters Using Fairchild Power Switch on www.fairchildsemi.com/an/AN/AN-4137.pdf
System Specifications Once the initial parameters of the power supply are known, the design can begin. These parameters include the min and max input voltage, input frequency, maximum output power, and estimated efficiency. From this, the initial system specifications can be calculated. The maximum input power can be determined by PIN = PO/Eff. The bulk capacitor can be estimated as 2-3µF per watt of input power for universal input range (85-265VRMS) and 1µF per watt of input power from European input range (195V-265VRMS).
using the cross sectional area of the core (Ae) and the saturation flux density (Bsat) which can be extracted from the B-H curves on the manufacturer’s datasheet. The turns ratio and resultant number of secondary turns for the transformer can then be found. Once the number of turn on the primary side is determined, the gap length of the core is calculated followed by the calculation of the wire diameter for each winding to make the transformer design is complete.
Output In its most basic form, the output structure of a flyback converter typically consists of a series rectifier diode and output capacitor placed in parallel with the output. There may be additional LC networks following this configuration for filtering purposes in the event that the ripple current specifications of the output capacitor cannot be met. To determine the output rectifier diode, the maximum reverse recovery voltage (VRRM) and the RMS current of the diode must be calculated. With that, a diode can be chosen from Fairchild’s diode selection guide.
Next, the maximum duty cycle can be determined. The duty cycle should be as large as possible providing there is enough margin in the MOSFET voltage rating.
When choosing the output capacitor, ensure that the calculated ripple current is smaller than the ripple current given on the capacitor’s datasheet. If a post filter is necessary, set the corner frequency from 1/10th to 1/5th of the FPS switching frequency.
Transformer and FPS Device
Snubber
Worst case conditions should be used when calculating the inductance for the primary side of the transformer (LM). For both continuous and discontinuous modes of operation, the worst case condition is at full load and minimum input voltage. Once LM is calculated, the maximum peak current (Idspeak) and RMS current (Idsrms) of the MOSFET in normal operation can be established. When choosing the FPS device for the design, it is important to make sure that the pulse-by-pulse current limit level (Iover) is greater than the maximum peak current of the MOSFET. Once the proper FPS device is chosen, the transformer can be designed. The first step is to choose the proper core depending on the input voltage range, number of outputs and switching frequency of the FPS device. The initial core selection will be somewhat rough due to the many variables involved, but the manufacturer’s core selection guide should be referred to when making this initial choice. With the selected core, calculate the minimum number of primary turns (NPmin) by
An RCD snubber network is needed when there is a high voltage spike on the drain of the FPS MOSFET when it is in the OFF state. This spike can lead to failure of the FPS device. The snubber network will clamp the voltage and protect the circuit. The first step is to determine the snubber capacitor voltage at the minimum input voltage and maximum load (Vsn). The power dissipated in the snubber network can then be calculated. The snubber resistor should be chosen with the proper wattage rating according to the power loss of the circuit. The capacitor voltage for the snubber is then calculated under maximum input and full load conditions. After choosing the snubber resistor and capacitor, the snubber diode can then be chosen. The maximum voltage stress on the MOSFET drain (Vdsmax) should be calculated and should be below 90% of the rated voltage of the MOSFET (BVdss). The voltage rating of the snubber diode should be higher than the MOSFET BVdss.
REV. 0.0.1 2/28/05
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AC/DC Switch Mode Power Supply Design Guide
Application Note Highlight
Design Guidelines for Off-Line Flyback Converters using Fairchild Power Switch (FPS™) (Continued) (AN-4137) Feedback loop Most FPS devices employ current mode control, therefore the feedback loop can be typically implemented with a one pole and one zero compensation circuit. Calculating the controlto-output transfer function origin is different depending on whether the circuit is operating in continuous or discontinuous mode. When a continuous mode converter design has multiple outputs, the low frequency control-to-output transfer function is proportional to the parallel combination of all of the load resistances, adjusted by the square of the turns ratio. Design of the feedback loop consists of the following steps. a) Determine the crossover frequency (fc). For CCM mode flyback, set fc below 1/3 of right half plane (RHP) zero to minimize the effect of the RHP zero. For DCM mode fc can be placed at a higher frequency, since there is no RHP zero.
b) When an additional LC filter is employed, the crossover frequency should be placed below 1/3 of the corner frequency of the LC filter, since it introduces a -180 degrees phase drop. Never place the crossover frequency beyond the corner frequency of the LC filter. If the crossover frequency is too close to the corner frequency, the controller should be designed to have a phase margin greater than 90 degrees when ignoring the effect of the post filter. c) Determine the DC gain of the compensator (wi/wzc) to cancel the control-to-output gain at fc. d) Place a compensator zero (fzc) around fc/3. e) Place a compensator pole (fpc) above 3fc.
For the complete Application Note, please visit us at www.fairchildsemi.com/an/AN/AN-4137.pdf www.fairchildsemi.com/acdc 27
REV. 0.0.5/05
AC/DC Switch Mode Power Supply Design Guide
Application Note Highlight
Power Factor Correction (PFC) Basics (AN-42047) What is Power Factor? Power Factor (PF) is defined as the ratio of the real power (P) to apparent power (S), or the cosine (for pure sine wave for both current and voltage) that represents the phase angle between the current and voltage waveforms (see Figure 1). The power factor can vary between 0 and 1, and can be either inductive (lagging, pointing up) or capacitive (leading, pointing down). In order to reduce an inductive lag, capacitors are added until PF equals 1. When the current and voltage waveforms are in phase, the power factor is 1 (cos (0°) = 1). The whole purpose of making the power factor equal to one is to make the circuit look purely resistive (apparent power equal to real power). Real power (watts) produces real work; this is the energy transfer component (example electricity-to-motor rpm). Reactive power is the power required to produce the magnetic fields (lost power) to enable the real work to be done, where apparent power is considered the total power that the power company supplies, as shown in Figure 1. This total power is the power supplied through the power mains to produce the required amount of real power.
When the power factor is not equal to 1, the current waveform does not follow the voltage waveform. This results not only in power losses, but may also cause harmonics that travel down the neutral line and disrupt other devices connected to the line. The closer the power factor is to 1, the closer the current harmonics will be to zero since all the power is contained in the fundamental frequency.
Understanding Recent Regulations In 2001, the European Union put EN61000-3-2, into effect to establish limits on the harmonics of the ac input current up to the 40th harmonic. Before EN61000-3-2 came into effect, there was an amendment to it passed in October 2000 that stated the only devices required to pass the rigorous Class D (Figure 2) emission limits are personal computers, personal computer monitors, and television receivers. Other devices were only required to pass the relaxed Class A (Figure 3) emission limits.
“Total Power” Apparent Power (S) = Volt Amperes = I2Z Reactive Power (Q) = vars = (XL – XC) | 2 θ Real Power (P) = Watts = (I2R)
Figure 2. Both Current and Voltage Waveforms are in Phase with a PF =1 (Class D)
Figure 1. Power Factor Triangle (Lagging)
The previously-stated definition of power factor related to phase angle is valid when considering ideal sinusoidal waveforms for both current and voltage; however, most power supplies draw a non-sinusoidal current. When the current is not sinusoidal and the voltage is sinusoidal, the power factor consists of two factors: 1) the displacement factor related to phase angle and 2) the distortion factor related to wave shape. Equation 1 represents the relationship of the displacement and distortion factor as it pertains to power factor. PF =
Irms(1) cos θ = Kd ⋅ Kθ Irms
Irms(1) is the current’s fundamental component and Irms is the current’s RMS value. Therefore, the purpose of the power factor correction circuit is to minimize the input current distortion and make the current in phase with the voltage.
Figure 3: This is What is Called Quasi-PFC Input, Achieving a PF Around 0.9 (Class A)
Refer to the complete application note, AN-42047, for additional information on: • Inefficiency causes • Boost converters • Modes of operation
For the complete Application Note, please visit us at www.fairchildsemi.com/an/AN/AN-42047.pdf
5/05
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AC/DC Switch Mode Power Supply Design Guide
Application Note Highlight
Choosing Power Switching Devices for SMPS Designs (AN-7010) This application note identifies the key parametric considerations for comparing IGBT and MOSFET performance in specific switch mode power supply (SMPS) applications. Parameters such as switching losses are investigated in both hard-switched and soft-switched zero voltage switching (ZVS) topologies. The three main power switch losses: turn-on, conduction and turn-off are described relative to both circuit and device characteristics. The differences in gate drive requirements are explained for the two voltage controlled products. Finally, the impact of the specific cooling system on device selection is explored.
pulses to measure EON. The first pulse raises the inductor to the desired test current and the second pulse then measures the EON loss recovering this current from the diode. FGH20N6S2D DIODE TA49469
L = 500µH
RG = 25Ω
Turn-On Losses
FGH20N6S2D
-
The turn-on characteristics of IGBTs and power MOSFETs are quite similar except that IGBTs have a longer voltage fall time. Referencing the basic IGBT equivalent circuit, Figure 1, the time required to fully modulate the minority carrier PNP BJT collector base region results in a turn-on voltage tail. Collector
PNP
Collector
Modulation
NPN
Gate
+
IGBT
Gate Rshorting
Body Region
Emitter
Emitter
Figure 1 - IGBT Equivalent Circuit This delay results in a Quasi-Saturation effect wherein the collector-emitter voltage does not immediately fall to its VCE(SAT) value1. This turn-on effect also results in a VCE voltage bump under ZVS conditions at the point where the load current transitions from the co-packed inverse parallel diode to the IGBT collector. The EON energy losses specified in datasheets is the time integral of Icollector times VCE in joules per switching cycle and includes the additional losses associated with quasi-saturation. Two EON energy parameters EON1 and EON2 are provided in IGBT datasheets. EON1 is the energy loss without the losses associated with hard-switched diode recovery. EON2 includes the hard-switched turn-on energy loss do to diode recovery. EON2 is measured recovering a diode identical to the co-packed diode associated with the device. A typical EON2 test circuit is illustrated in Figure 2. The test is performed with the diode at the same Tj as the DUT. The IGBT is switched through two
VDD = 390V
Figure 2 - Typical EON and EOFF Test Circuit Under hard-switched turn-on the gate drive voltage and impedance and the recovery characteristics of the commutated diode determine the EON switching loss. For circuits such as the conventional CCM boost PFC circuit the boost diode recovery characteristics are extremely important in controlling EON (turn-on) energy losses. In addition to selecting a boost diode with minimal Trr and QRR it is also important to ensure that the diode has soft recovery characteristics. Softness, the ratio of tb/ta, has a considerable impact on the electrical noise and voltage spikes generated across the switching device. Snappy diodes with a high tb period di/dt fall from IRM(REC) create large voltage spikes in the circuit parasitic inductances. These voltage spikes create EMI and can result in excessive reverse voltage across the diode. In hard-switched circuits such as the full-bridge and half bridge topologies where the IGBT co-packed or MOSFET body diodes are conducting when the alternate switching device is turned on, the diode recovery characteristics determine the EON loss. For this reason it is important to select MOSFETs with Fast body diode recovery characteristics such as the Fairchild FQA28N50F FRFET™. Unfortunately, MOSFET parasitic or body diodes are relatively slow compared to state-of-the-industry discrete diodes. For hard-switched MOSFET applications the body diode is often the limiting factor determining the SMPS operating frequency. Typically IGBT co-packed diodes are selected for compatibility with their intended applications. Slower Ultrafast diodes with lower forward conduction losses are co-packed with slower lower VCE(SAT) motor drive IGBTs. Conversely soft
5/05
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AC/DC Switch Mode Power Supply Design Guide
Application Note Highlight
Choosing Power Switching Devices for SMPS Designs (Continued) (AN-7010) recovery Hyperfast diodes such as the Fairchild Stealth™ series are co-packed with the high frequency SMPS2 switched mode IGBTs. Beyond selecting the right diode the designer can control Eon losses by adjusting the gate drive turn-on source resistance. Decreasing the drive source resistance will increase the IGBT or MOSFET turn-on di/dt and decrease the Eon loss. The tradeoff is between Eon losses and EMI since the higher di/dt will result in increased voltage spikes and radiated and conducted EMI. Selecting the correct gate drive resistance to meet a desired turn-on di/dt may require in-circuit testing and verification. A ballpark value may be determined from the MOSFET transfer curve, Figure 3. Assuming the FET current will rise to 10A at turn-on and looking at the 25°C curve of Figure 3, the gate voltage must transition from 5.2V to 6.7V to reach the 10A and the average GFS is (10A/6.7V - 5.2V) = 6.7Ω.
Similar Gate drive turn-on resistance may be calculated for the IGBT. Again VGE(avg) and GFS may be determined from the IGBT transfer characteristic curve and the CIES value at VGE(avg) should be substituted for Ciss. The comparable calculated IGBT turn-on gate drive resistance is 100Ω. This higher ohm requirement is indicative of the higher IGBT GFS and lower CIES. A key point here is that gate drive circuit adjustments must be made for a transition from MOSFET to IGBT. Refer to the complete application note, AN-7010, that continues with the comparisons between MOSFETs and IGBTs on the following subjects: • Conduction losses • Turn off losses • Gate drive requirements • Thermal management
ID, Drain Current (A)
1 101 150°C 25°C
100
Pittet, Serge and Rufer, Alfred "Analytical analysis of Quasi-Saturation Effect in PT and NPT IGBTs" PCIM Europe 2002 http://leiwww.epfl.ch/publications/pittet_rufer_pcim_02.pdf
-55°C
NOTE 1. VDS = 40V 2. 250µs Pulse Test
10-1
2
4 6 8 VGS, Gate-Source Voltage (V)
10
Figure 3 - FCP11N60 Transfer Characteristics Rgate = [Vdrive - VGS(avg)] •
GFS (di/dt) • Ciss
Eq. 1 - Gate drive resistance for desired turn-on di/dt Applying this average GFS value to Equation 1 with a gate drive of Vdrive = 10V, a desired di/dt = 600 A/µs and typical FCP11N60 values VGS(avg) = 6V, Ciss = 1200pF; a 37Ω turn-on gate drive resistance is calculated. Since the instantaneous GFS value is the slope in Figure 3 curves, GFS will vary during the Eon period, which implies a varying di/dt. The exponentially decaying gate drive current and decreasing Ciss as a function of VFS also enter into this equation with an overall effect of surprisingly linear current rise.
For the complete Application Note, please visit us at www.fairchildsemi.com/an/AN/AN-7010.pdf
REV. 0.0.1 3/05
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AC/DC Switch Mode Power Supply Design Guide
Global Power Resource™ Fairchild provides customers with resources to help dramatically reduce design cycle times by offering world-wide customer design labs, and advanced web-based design tools, tutorials and other application-specific on-line information. • Design and selection tools • Tutorials • On-demand training • Evaluation boards/reference designs • For a complete list of available resources, visit us at www.fairchildsemi.com/acdc
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AC/DC Switch Mode Power Supply Design Guide
Notes
www.fairchildsemi.com/acdc 32
For a complete listing of sales representatives and sales offices, visit www.fairchildsemi.com/cf/sales_contacts/ Americas Fairchild Semiconductor Customer Response Center 7701 Las Colinas Ridge, Suite 400 Irving, Texas 75063 United States China Fairchild Semiconductor (Shanghai) Company Limited Bejing Liaison Office Room 2506, China Resources Building No. 8, Jianguomenbei Avenue Beijing 100005, P.R. China Tel: 86-10-8519-2060 Fax: 86-10-8519-2061 Fairchild Semiconductor (Shanghai) Company Limited Shenzhen Liaison Office Room 1506, China Resources Building 5001 Shen Nan Road East Shenzhen 518008, P.R. China Tel: 86-755-8246-3088 Fax: 86-755-8246-2092 Fairchild Semiconductor (Shanghai) Company Limited Puxi Liaison Office Room 2208, Kerry Centre No. 1515 Nanjing West Road Jingan, Shanghai 200040 P.R. China Tel: 86-21-5298-6262 Fax: 86-21-5298-5118/9 Fairchild Semiconductor (Shanghai) Company Limited Chengdu Liaison Office Unit 603, Block A Fuhe Business Incubation Base Chengdu Hi-Tech Zone Innovation Service Center 12 Gaopeng Road Chengdu 610041, Sichuan P.R. China Tel : 86-28-8515-1709 Fax : 86-28-8515-2604 Fairchild Semiconductor (Shanghai) Company Limited Xiamen Liaison Office Unit D, 14/F, International Plaza 8 Lujiang Road Xiamen 361001, Fujian P.R. China Tel : 86-592-2101-688 Fax : 86-592-2101-678 Fairchild Semiconductor (Shanghai) Company Limited Qingdao Liaison Office Room 20D Hua Ren International Building 2 Jia Shandong Road Qingdao 266071, Shandong P.R. China Tel : 86-532-3096-550 Fax : 86-532-3096-551
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